Determination of Array Gain of Single Hop to Achieve the Performance of a 2-Hop Wireless Link

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1. Introduction

To combat the fading affect of long wireless link, 2-hop model is widely used where a relay is placed between transmitter and receiver. The concept is applicable to enhance the performance of point to point link. The combined SNR of two links becomes approximately parallel combination of two SNRs like equivalent parallel resistor of electrical circuit. Therefore the combined SNR is less than the individual SNR (between transmitter and repeater or repeater and receiver) but the SNR between the transmitter and receiver (without the repeater station) is much less than the combined SNR of 2-hop wireless link. This phenomenon attracts the researcher to apply the concept of multi-hop in wireless networks to reduce SER and enhance throughput. The performance analysis of two-hop wireless link in context of BER under fading is discussed in [1] [2] [3] [4] . Usually in rural or suburban area the gain of the relay is kept constant called amplify-and-forward (AF) relaying. In a dense urban area the wireless link is found as time selective channel i.e. SNR of receiver varies with time hence the gain of the relay has to be adjusted with feedback signal like adaptive algorithm of digital filter. The concept of AF and DF relay is found in [5] [6] [7] where the idea of channel state information is included. In [8] , authors analyzed performance of AF relay network where relay is affected by interferences under assumption that there is no obstacle between interferences and relay i.e. LOS interferences. The paper derived closed form solution of outage probability with the idea of [9] [10] . To reduce BER of 3G mobile cellular destined for high speed communication needs to overcome small scale fading (Rayleigh fading). In this context selection of best relay is discussed in [11] with MIMO (multiple input multiple output). Actually MIMO is used in wireless link to take the advantage of space diversity at the expense of system cost. Different combination of MIMO (both the hop is MIMO, MISO in first hop and SIMO in second hop, SIMO in first hop and MISO in second hop etc.) is found in recent literature for 2-hop wireless link [11] [12] [13] .

The main objective of AAS is to combine the radiation pattern of individual antenna element (with proper weighting factor and phase shift) to produce a combined beam of desired directivity and gain. The detail analysis of AAS is found in [14] [15] [16] . To make the system dynamic, adaptive beam forming algorithm is used to select the appropriate weighting factor of antenna elements. Several applications of AAS for example: Beam Steering and Switching, Conventional Beam Forming, Diversity Combining, Array on Satellites, Dynamic beams, Reduction in Delay Spread and Multipath Fading, Reduction in Co-channel Interference etc. are discussed in [14] . The same author discussed detail about mathematical model and adaptive algorithms of conventional beam former, null-steering beam former, optimal beam forming, broad-band beam forming, frequency-domain beam forming, SMI algorithm, LMS algorithm, RLS algorithm, MVDR estimator etc in [15] . In this paper we make a comparison of 2-hop wireless link under single antenna system with the case of direct wireless link (without relay) of array antenna system (AAS) to reduce complexity of communication system. Two most important features of 5G mobile communication are: “Ultra-Dense Networks (UDN)” and “massive MIMO” hence multi-hop wireless link will make the system very complex. The objective of the paper is to acquire the capacity of single hop link equivalent to dual hop link. The adaptive beamformer can only help us to achieve the goal.

The paper is organized like: Section 2 provides the theoretical analysis of dual-hop wireless link in determination of overall SNR, Section 3 deals with concept of AAS, overall SINR (signal to interference and noise ratio) at receiving end and algorithms of adaptive beamforming; Section 4 provides the results based on theoretical analysis of Section 3; and Section 5 concludes the entire analysis.

2. Dual-Hop Wireless Link

First of all we consider the 2-hop wireless link of Figure 1 where the SNR between transmitter and relay is Γ_{SR} and that of relay to destination is Γ_{RD}.

The received signal vector at the relay is expressed as:

${y}_{R}=\sqrt{E}{H}_{SR}x+{n}_{SR}$ , (1)

where E is the transmitted power, ${H}_{SR}$ is the channel matrix from the source to relay, x is the signal vector of source, and ${n}_{SR}$ is the noise vector of source to relay link. Above expression is applicable for MIMO system but for single antenna system instead of signal vector we consider individual symbol (for example symbols of 16-QAM) of transmitter and instead of channel matrix we consider simply channel gain may be complex number. When the signal is detected at relay, it is processed and transmitted with some delay expressed as: ${{y}^{\prime}}_{RD}$ hence the received signal vector at the destination is,

${y}_{D}=\sqrt{E}{H}_{RD}{{y}^{\prime}}_{RD}+{n}_{RD}$ (2)

The noise vector on both the links are uncorrelated and possesses the properties:
${\rm E}\left({n}_{SR}{n}_{SR}^{\text{\u2020}}\right)={I}_{{N}_{R}}{N}_{0}$ and
${\rm E}\left({n}_{RD}{n}_{RD}^{\text{\u2020}}\right)={I}_{{N}_{D}}{N}_{0}$ , where
${N}_{0}$ is the variance of the additive white Gaussian noise (AWGN),
${I}_{{N}_{R}}$ is the identity matrix with N_{R} antennas at the relay station and N_{D} is the number of antennas at the destination.

If the SNR of the links are: ${\Gamma}_{SR}={E}_{S}{\Vert {H}_{SR}\Vert}^{2}/{N}_{0}$ and ${\Gamma}_{RD}={\stackrel{\xaf}{E}}_{R}{\Vert {H}_{RD}\Vert}^{2}/{N}_{0}$ , then the overall SNR will be [4] [11] :

${\Gamma}_{SD}=\frac{{\Gamma}_{SR}{\Gamma}_{RD}}{{\Gamma}_{SR}+{\Gamma}_{RD}+1}$ (3)

This overall SNR will be compared with overall SNR of AAS with adaptive beamformer under single hop of same path length.

For single antenna case Equations (1) and (2) is written conventionally like:

${y}_{R}=\sqrt{P}{h}_{SR}x+{n}_{SR}$ (4)

${y}_{D}=\sqrt{P}{h}_{RD}{{y}^{\prime}}_{R}+{n}_{RD}$ (5)

where each variable indicates a real or complex number instead of vector.

Figure 1. Dual-hop wireless link.

Once combined SNR ${\gamma}_{c}={\Gamma}_{SD}$ is evaluated then the SER under awgn is expressed as [8] ,

${P}_{s}\left({\gamma}_{c}\right)=aQ\left(\sqrt{2b{\gamma}_{c}}\right)$ (6)

where ${\gamma}_{c}$ is a r.v. and the integers a and b depend on type of modulation scheme. Above analysis under fading channel is expressed as,

${P}_{s}\left({\gamma}_{c\_av}\right)={\displaystyle \underset{0}{\overset{\infty}{\int}}{P}_{s}\left({\gamma}_{c}\right){f}_{{\Gamma}_{c}}\left({\gamma}_{c},{\gamma}_{c\_av}\right)\text{d}{\gamma}_{c}}$ (7)

where ${f}_{{\Gamma}_{c}}\left({\gamma}_{c},{\gamma}_{c\_av}\right)$ is the pdf of r.v. of small scale fading channel and ${\gamma}_{c\_av}$ is the average value of the r.v. In this paper we consider only Nakagami-m fading channel. For example for Nakagami-m fading case the pdf becomes,

${f}_{{\Gamma}_{c}}\left({\gamma}_{c},{\gamma}_{c\_av}\right)=\frac{{m}^{m}{\gamma}_{c}^{m-1}}{{\gamma}_{c\_av}^{m}\Gamma \left(m\right)}{\text{e}}^{-m{\gamma}_{c}^{2}/{\gamma}_{c\_av}}$ (8)

We can use Equations (7) and (8) to evaluate SER under Nakagami-m fading case.

3. Adaptive Beamforming

In array antenna system the number of antenna elements is a vital factor to achieve a wide variation of directivity and gain visualized from Figure 2; where a linear array is considered with spacing of antenna elements of half wavelength i.e. λ/2.

Extraction of the original signal from a noisy environment is achieved by Finite Impulse Response (FIR) or Infinite Impulse Response (IIR) filter but their coefficients remain fixed during entire operation. In adaptive filter, adaptive

Figure 2. Radiation pattern of linear array taking spacing of array elements λ/2.

algorithms are used to adjust the coefficients of the digital filter so that the difference between the noisy input signal, X_{k} and the desired signal, d called the error signal ε attains at minimum value. The common algorithms found widespread applications are the least mean square (LMS), the recursive least squares (RLS), and the Kalman filter algorithms. In terms of computational complexity and storage requirements, the LMS algorithm is the most efficient but the Kalman filter is suitable for immunity of any type of noise at the expense of process time. To enhance the gain of the antenna array in the direction of desired signal and to provide attenuation in the direction of interference or multiple jammer we use adaptive algorithm of IIR and FIR filter. An adaptive filter consists of FIR/IIR and adaptive algorithm to adjust the weighting factor of each branch of signal discussed in [17] [18] , such concept in AAS is called adaptive beamforming. The following two sub-sections will provide the basic concept of adaptive beamforming technique where the concept is available in [19] [20] .

Let us now provide the way of enhancement of gain in desired direction and elimination of jammers using the concept of adaptive beamforming. We will then determine the threshold gain of the beamformer under a single hop wireless link to be comparable with case of 2-hop link in context of SER. In adaptive beam former two types of omni antennas are used 1) primary antenna 2) reference antenna. Both types of antennas receive signal and interference/jammer. Each reference antenna element is associated with adaptive filter and its weight is adjusted in such a way that it can receive only jammer where the primary antenna provides the sum of signal and jammer. Now the jammer part of the primary antenna is correlated with the output of reference antenna hence the error between primary and reference antenna provides the required signal component. The weighting factors of reference antenna elements are updated using adaptive algorithms of [21] .

To match with multiple jammers of different direction at the same time, it is necessary to have more than one reference omni as explained in [22] [23] . Figure 3 shows the arrangement of such antenna system considering two spatially separated reference omnis.

Radiation pattern of two reference adaptive beamforming is shown in Figure 4 taking the weighting factors as: ${w}_{11}=-0.48$ , ${w}_{12}=-0.871$ , ${w}_{21}=1.7$ and ${w}_{22}=1$ based on [24] . Here the null forms along 30˚, 150˚, 60˚ and 120˚; where the main beam is directed along 270˚.

The overall SINR at receiving end is, ${\Gamma}_{0}=\frac{{P}_{r}\cdot {G}_{d}}{{\displaystyle \underset{j=1}{\overset{k}{\sum}}{I}_{j}\cdot {A}_{j}}+{N}_{0}}\approx \Gamma \cdot G$ (9)

where P_{r} is the received signal power along desired direction, G_{d} is gain of the AAS along the link between T_{x} and R_{x}, A_{j} is the gain along the jth jammer, I_{j} is the interference/jammer along jth direction and N_{0} is the awgn noise. Overall SINR is approximated as
$\Gamma \cdot G$; where Γ is the SNR of conventional single antenna system and G is the ratio of G_{d} and A_{j}.

Figure 3. Side lobe canceller with two incident signals.

Figure 4. Radiation pattern of two reference antenna system.

In free space path loss model the received signal at a distance d is expressed as:
${P}_{r}=K\cdot {P}_{t}\cdot {d}^{-\alpha}$; where α is path-loss exponent. Therefore if the distance is increased to twice of the previous one then the received signal or SNR is decreased by a factor of 2^{−}^{α}. The overall SNR of 2-hop wireless link (distance of each is d) is approximately half of SNR of single hop link of distance d. If the enhancement of overall gain G of the array antenna system is greater than 2^{−α-}^{1} then the proposed scheme of the thesis brings the desired result will be verified in next section. Such concept is available in [25] [26] in a different way. In real life the situation is the analysis becomes more complicated due to large scale fading (modeled by Okumura-Hata/Walfish-Ikegami/Lee) and small scale fading (modeled by FIR filter with appropriated fading parameters).

3.1. Algorithm-1

In this algorithm we use the concept of Wiener filter theory in minimization of mean square error of cost function which actually represents the difference between output of the adaptive filter and desired output. For input signal u(n) and kth weighting factor W_{k} the output signal from a linear combiner is given as,

$y\left(n\right)={\displaystyle \underset{k=0}{\overset{M-1}{\sum}}{W}_{k}^{*}u\left(n-k\right)}$ (10)

Output power,

$P={\left|y\left(n\right)\right|}^{2}={\displaystyle \underset{k=0}{\overset{M-1}{\sum}}{\displaystyle \underset{i=0}{\overset{M-1}{\sum}}{W}_{k}^{*}{W}_{i}E\left[u\left(n-k\right)u\left(n-i\right)\right]}}={\displaystyle \underset{k=0}{\overset{M-1}{\sum}}{\displaystyle \underset{i=0}{\overset{M-1}{\sum}}{W}_{k}^{*}{W}_{i}r\left(i-k\right)}}$ (11)

where $E\left[u\left(n-k\right)u\left(n-i\right)\right]=r\left(i-k\right)$ is the autocorrelation function.

If the beamformer is subjected to a linear constraint, $\underset{k=0}{\overset{M-1}{\sum}}{W}_{k}^{*}{\text{e}}^{-j{\theta}_{0}k}}=g$; then

the real valued cost function becomes,

$J={\displaystyle \underset{k=0}{\overset{M-1}{\sum}}{\displaystyle \underset{i=0}{\overset{M-1}{\sum}}{W}_{k}^{*}{W}_{i}r\left(i-k\right)}}+\mathrm{Re}\left[{\lambda}^{*}\left({\displaystyle \underset{k=0}{\overset{M-1}{\sum}}{W}_{k}^{*}{\text{e}}^{-j{\theta}_{0}k}-g}\right)\right]$ (12)

where g is the complex-valued gain, θ_{0} desired electrical angle of arrival.

Taking gradient of J and putting the result equal to zero like Wiener filter theorem, we get the optimum weighting vector like,

${W}_{0}=\frac{{g}^{*}{R}^{-1}S\left({\theta}_{0}\right)}{{S}^{H}\left({\theta}_{0}\right){R}^{-1}S\left({\theta}_{0}\right)}$ (13)

where $S\left({\theta}_{0}\right)=\left[\begin{array}{ccccc}1& {\text{e}}^{-j{\theta}_{0}}& {\text{e}}^{-j2{\theta}_{0}}& \cdots & {\text{e}}^{-j\left(M-1\right){\theta}_{0}}\end{array}\right]$ is known as steering vector and its details are found in [27] [28] [29] .

Considering uniform linear array of N = 6 antenna elements the variation of normalized power (dB) against the azimuth angle is shown in Figure 3 taking the AOA of: azimuth 60˚, elevation 15˚ and carrier frequency of f_{c} = 1 GHz. The response is found different after inclusion of steering vector, visualized the Figure 5.

The steering vector corresponding to Figure 5 is,

$\begin{array}{c}S=[\begin{array}{ccc}-0.9971-0.0760i& 0.8350-0.5503i& -0.3234+0.9462i\end{array}\\ \text{\hspace{0.17em}}\text{\hspace{0.17em}}\text{\hspace{0.05em}}\text{\hspace{0.05em}}{\begin{array}{ccc}-0.3234-0.9462i& 0.8350+0.5503i& -0.9971+0.0760i\end{array}]}^{\text{T}}\end{array}$

3.2. Algorithm-2

This algorithm is an extension of previous one where the desired and undesired signals are analyzed separately. A widely used method of adaptive beamforing is LCMV (linearly constraint minimum variance) algorithm where the weighting vector of adaptive filter is divided into two portion W_{q} and W_{a}. Here the first one is dependent on desired signal i.e. signal along the desired AOA (Angle of Arrival) and the second one is related to sidelobe and un-correlated with the desired signal. A constraint matrix C_{a} correspond to a band rejection filter is used to segregate the sidelobe from the desired signal shown in Figure 6. Finally

Figure 5. The profile of normalized power against azimuth angle.

Figure 6. Adaptive beamformer with LCMV.

Winner filter theorem is applied to in getting weighting vector for minimum output y(n).

Let us introduce multiple linear constraints by the constraint matrix C and gain vector g like,

${C}^{H}W=g$ (14)

where the overall weight vector is, $W={W}_{q}-{C}_{a}{W}_{a}$

The desired signal of the beamformer,

$d\left(n\right)={W}_{q}^{H}\cdot U\left(n\right)$; where ${W}_{q}=C{\left({C}^{H}C\right)}^{-1}g$ (15)

If C_{a} is a stop band FIR filter with zero response in desired direction θ_{0} then the signal with sidelobe is
${C}_{a}^{H}U\left(n\right)=x\left(n\right)$ and the output signal is
$y\left(n\right)=d\left(n\right)-{W}_{q}^{H}x\left(n\right).$

Applying Winner filter theorem,

${W}_{a}={\left({C}_{a}^{H}R{C}_{a}\right)}^{-1}{C}_{a}^{H}R{W}_{q}$ (16)

where R is the autocorrelation matrix of input vector.

Taking the following parameters under LCMV: SNR = 50 dB, carrier frequency f_{c} = 1 GHz, the number of antenna elements N = 10, antenna spacing λ/2 and elevation angles 0˚ we get the following response (using simulation of LCMV in Matlab 13) for different AOA and directions of jammer (azimuth angle) shown in Figure 7. Such concept is available for both linear and circular array in [30] .

The weighting vectors for above 4 cases are evaluated as:

$\begin{array}{l}{W}_{1}=[\begin{array}{cccc}-0.0489-0.1267i& 0.0443+0.1161i& -0.0540-0.0985i& 0.0322+0.0688i\end{array}\\ \text{\hspace{0.17em}}\text{\hspace{0.17em}}\text{\hspace{0.17em}}\text{\hspace{0.17em}}\text{\hspace{0.17em}}\text{\hspace{0.17em}}\text{\hspace{0.17em}}\begin{array}{cccc}-0.0176-0.1005i& -0.0264+0.0665i& 0.0128-0.0669i& -0.0613+0.1043i\end{array}\\ \text{\hspace{0.17em}}\text{\hspace{0.17em}}\text{\hspace{0.17em}}\text{\hspace{0.17em}}\text{\hspace{0.17em}}\text{\hspace{0.17em}}\text{\hspace{0.17em}}{\begin{array}{cc}0.0407-0.1328i& -0.0558+0.1188i\end{array}]}^{\text{T}}\end{array}$

$\begin{array}{l}{W}_{2}=[\begin{array}{cccc}0.0680-0.0776i& 0.0364+0.0809i& -0.0568+0.0648i& -0.0782-0.0738i\end{array}\\ \text{\hspace{0.17em}}\text{\hspace{0.17em}}\text{\hspace{0.17em}}\text{\hspace{0.17em}}\text{\hspace{0.17em}}\text{\hspace{0.17em}}\text{\hspace{0.17em}}\begin{array}{cccc}0.0767-0.0872i& 0.0847+0.0737i& -0.0767+0.0672i& -0.0731-0.0556i\end{array}\\ \text{\hspace{0.17em}}\text{\hspace{0.17em}}\text{\hspace{0.17em}}\text{\hspace{0.17em}}\text{\hspace{0.17em}}\text{\hspace{0.17em}}\text{\hspace{0.17em}}{\begin{array}{cc}0.0619-0.0593i& 0.0786+0.0830i\end{array}]}^{\text{T}}\end{array}$

$\begin{array}{l}{W}_{3}=[\begin{array}{cccc}0.0452-0.0686i& -0.0665+0.0640i& 0.0487-0.0840i& -0.0318+0.0945i\end{array}\\ \text{\hspace{0.17em}}\text{\hspace{0.17em}}\text{\hspace{0.17em}}\text{\hspace{0.17em}}\text{\hspace{0.17em}}\text{\hspace{0.17em}}\text{\hspace{0.17em}}\begin{array}{cccc}0.0142-0.1566i& -0.0035+0.1070i& -0.0446-0.0866i& 0.0445+0.0989i\end{array}\\ \text{\hspace{0.17em}}\text{\hspace{0.17em}}\text{\hspace{0.17em}}\text{\hspace{0.17em}}\text{\hspace{0.17em}}\text{\hspace{0.17em}}\text{\hspace{0.17em}}{\begin{array}{cc}-0.0491-0.0701i& 0.0633+0.0493i\end{array}]}^{\text{T}}\end{array}$

$\begin{array}{l}{W}_{4}=[\begin{array}{cccc}-0.0009-0.0962i& -0.0208+0.0956i& -0.0021-0.1051i& 0.0014+0.0879i\end{array}\\ \text{\hspace{0.17em}}\text{\hspace{0.17em}}\text{\hspace{0.17em}}\text{\hspace{0.17em}}\text{\hspace{0.17em}}\text{\hspace{0.17em}}\text{\hspace{0.17em}}\begin{array}{cccc}-0.0004-0.1425i& -0.0111+0.0963i& -0.0161-0.0788i& -0.0055+0.1134i\end{array}\\ \text{\hspace{0.17em}}\text{\hspace{0.17em}}\text{\hspace{0.17em}}\text{\hspace{0.17em}}\text{\hspace{0.17em}}\text{\hspace{0.17em}}\text{\hspace{0.17em}}{\begin{array}{cc}-0.0096-0.1043i& 0.0049+0.0833i\end{array}]}^{\text{T}}\end{array}$ ^{ }

4. Results

In this paper the matric used against the performance of wireless link is SER or

Figure 7. The response of LCMV beamformer under linear array of 10 antenna elements.

BER for single and 2-hop cases. Figure 8 shows the profile of SER against average SNR for both 2-hop link and single hop link of same path length incorporating AAS of two antenna elements. Here our proposal becomes successful when overall gain (enhancement of desired signal and attenuation of interferences) G is greater than or equal to 3.44 dB for Nakagami-m fading with m = 4. In Figure 8 we found that SER of single hop is better than the case of 2-hop for G = 4.77 and 6.02 dB but worse than it for G = 3.42 dB. In case of Rayleigh fading the threshold gain G becomes 1.86 visualized from Figure 9 where the SER is found better than 2-hop for G = 1.76, 4.77 and 6.02 dB but worse than it for G = 1.76 dB.

Figure 8. The comparison of SER under 2-hop link and single link with AAS for Nakagami-m fading.

Figure 9. The comparison of SER under 2-hop link and single link with AAS for Rayleigh fading case.

Finally we compare the theoretical and simulation results regarding 2-hop and single hop AAS under QPSK modulation scheme. We use Rayleigh and Nakagami-m fading condition with bit rate of 9.6 Kbps and Doppler shift of 100 Hz. First the simulation is done for 2000 random symbols shown in Figure 10(a) then for 200,000 symbols shown in Figure 10(b). The simulation curves become smothering for more symbols validates the concept Monte Carlo simulation. The similar result is shown in logarithmic scale in Figure 10(c). The difference between simulation and theoretical result is less than 5% hence ensure 95% confidence level. All the curves reveal the success of our proposed scheme when we use G = 1.86 under the simulation as well. Similar job is done for Nakagami-m fading case shown in Figures 11(a)-(c).

The relative performance between Rayleigh and Nakagami-m is found subtle for SNR in the range of 0 dB to 20 dB. To observe the variation we plot BER

Figure 10. Comparison of 2-hop and AAS with simulation for Rayleigh fading case.

Figure 11. Comparison of 2-hop and AAS with simulation for Nakagami-m fading case.

against SNR in the range of −10 dB to 0 dB shown in Figure 12(a) and Figure 12(b); where the performance under Nakagami-m fading is found better than that of Rayleigh case because of strong link between transmitter and receiver for former case. Finally the performance of AAS is found better than conventional 2-hop wireless link for SNR in the range of 0 dB to 20 dB visualized from Figure 10 and Figure 11. Situation is found reverse for SNR in the range of −10 dB to 0 dB shown in Figure 12(a) and Figure 12(b) taking the same overall array gain. To overcome the above cumbersome situation the array gain has to be changed at low SNR condition even we have to consider the environment of fading.

5. Conclusion

The weak radiation of the antenna is strengthened and made more directional using antenna array. The performance of single hop link is compared with 2-hop

Figure 12. Comparison of 2-hop link and AAS at low SNR.

link of same distance using adaptive array antenna system. The results of the paper highlighted the threshold gain of the array required to meet the condition of 2-hop wireless link. In this paper we use exponential path loss model suitable for suburban area or a link of short distance applicable in ad-hoc network or femto cell of LTE. Still we have the scope to enhance the model for conventional path loss model of fading channel. The analysis of the paper will be helpful for a wireless network planner to choose the optimum antenna for coverage of WLAN and WMAN.

Conflicts of Interest

The authors declare no conflicts of interest regarding the publication of this paper.

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https://doi.org/10.4236/jemaa.2015.74014